Active electromagnetic interference filter with damping network

ABSTRACT

In some examples, a circuit includes an amplifier, a resistor, and a damping network. The amplifier has an amplifier output and first and second amplifier inputs. The first amplifier input is adapted to be coupled to a first terminal, and the second amplifier input is configured to receive a reference voltage. The resistor is coupled between the amplifier output and the first amplifier input. The damping network is coupled between the amplifier output and the first terminal.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application claims priority to U.S. Provisional Patent ApplicationNo. 62/827,699, which was filed Apr. 1, 2019, is titled “ELECTROMAGNETICINTERFERENCE (EMI) FILTERS WITH DAMPING NETWORK,” and is herebyincorporated herein by reference in its entirety.

BACKGROUND

A switched mode power supply (SMPS) transfers power from an input powersource to a load by switching one or more power transistors. Thetransistors are coupled through a switch node/terminal to an energystorage element (such as an inductor/transformer and/or capacitor) thatis capable of coupling to the load. The power transistors can beincluded in a power converter that includes, or is capable of couplingto, the energy storage element. An SMPS can include an SMPS controllerto provide one or more gate drive signals to the power transistor(s).The switching on and off of the power transistors sometimes createsnoise on a signal line, such as an input voltage line, that can presentas electromagnetic interference that can at times be detrimental orundesirable.

SUMMARY

The amplifier has an amplifier output and first and second amplifierinputs. The first amplifier input is adapted to be coupled to a firstterminal, and the second amplifier input is configured to receive areference voltage. The resistor is coupled between the amplifier outputand the first amplifier input. The damping network is coupled betweenthe amplifier output and the first terminal.

In at least some examples, a system includes a power source, a filter, apower converter, and an active electromagnetic interference filter(AEF). The filter has a filter input and a filter output. The filterinput is coupled to the power source. The power converter is configuredto switch power from the output terminal of the filter to a load.Switching the power from the output terminal of the filter to the load,in some examples, generates noise at the power source. The AEF iscoupled to the power source and comprises a damping network. The AEF isconfigured to reduce a magnitude of the noise. The damping network isconfigured to make the AEF less capacitive from a perspective of thefilter.

In at least some examples, a circuit includes an AEF and a dampingnetwork coupled to the AEF. The AEF is configured to sense a noisevoltage of noise at a terminal, the noise including low frequency noisecomponents and high frequency noise components. The AEF is furtherconfigured to generate a cancellation signal according to a differencebetween the noise voltage and a reference voltage. The AEF is furtherconfigured to inject the cancellation signal into the terminal. Thedamping network is configured to make the AEF less capacitive responsiveto the low frequency noise components.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows a block diagram of an illustrative switched mode powersupply (SMPS) in accordance with various examples.

FIG. 2 shows a schematic diagram of an illustrative activeelectromagnetic interference filter (AEF) in accordance with variousexamples.

FIG. 3 shows a diagram of illustrative signal waveforms in accordancewith various examples.

FIG. 4 shows a diagram of illustrative signal waveforms in accordancewith various examples.

DETAILED DESCRIPTION

In some architectures (such as buck-boost architectures), a switchedmode power supply (SMPS) includes, or is capable of coupling to, anoutput/bulk capacitor in parallel with a load. A SMPS controllerswitches the power transistor(s) to form circuit arrangements withenergy storage element(s) to supply a load current to the load and/or tothe output/bulk capacitor to maintain a regulated output voltage (e.g.,by filtering the switched load current). For example, a power transistorcan be coupled through the switch node/terminal to an energy storageinductor. The energy storage inductor is switched by the SMPS controllerbetween charge and discharge cycles to supply inductor current (e.g.,current through the energy storage inductor) to the load and to theoutput/bulk capacitor to filter the inductor current to maintain theregulated output voltage. In some examples, an SMPS can be configuredfor operation as a constant current source with an energy storageelement but with no output/bulk capacitor.

The power transistors can be implemented as metal oxide semiconductorfield effect transistors (MOSFETs) or any other suitable solid-statetransistor devices (e.g., bi-polar junction transistors (BJTs)). As aninput voltage (VIN) or an output voltage (VOUT) of the power convertervaries, the SMPS controller may control the power converter to operatein different modes of operation.

To control a mode of operation of the power converter, the SMPScontroller provides gate control signals to one or more powertransistors of the power converter. A value of each of these gatecontrol signals determines whether a respective power transistorreceiving the gate control signal is in a conductive state (e.g., turnedon) or in a non-conductive state (e.g., turned off). To change a mode ofoperation of the power converter, the SMPS controller modifies a valueof one or more of the gate control signals to turn one or more of thepower transistors on or off. Also, while remaining in a mode ofoperation of the power converter, the SMPS controller may modify a valueof one or more of the gate control signals, for example, toalternatively turn on and turn off one or more power transistors.

Generally, the SMPS controller controls the power converter to operateat a particular switching frequency. Some switching frequencies, such ashigh switching frequencies (e.g., greater than about 1.8 megahertz(MHz)), enable a smaller physical footprint of the power converterand/or SMPS controller by enabling the use of smaller circuitcomponents. Other switching frequencies, such as low switchingfrequencies (e.g., less than about 500 kilohertz (kHz)), enableincreased efficiency of a power converter by reducing switching lossesof the power converter. The switching of the power transistors on andoff, in at least some examples, creates noise in the SMPS and/or on asignal line, component, circuit, or device coupled to the SMPS. In somecircumstances, this noise presents itself as electromagneticinterference (EMI), such as on power lines over which the SMPS receivesVIN from a power source. The noise, in at least some examples, affectsthe power source such that other devices receiving power from the powersource over other power lines may be affected by the noise. Accordingly,it is at least sometimes desirable to cancel or otherwise mitigate thenoise.

Various filtering techniques exist for mitigating the noise. Some ofthese filtering techniques are passive, such as resistor-capacitor (RC)filters or inductor-capacitor (LC) filters. Other filtering techniquesare active, such as an active EMI filter (AEF). Some implementations ofan AEF include an operational amplifier that senses the noise (e.g.,such as a voltage of the noise) and generates a signal (e.g., such as acancellation voltage) to compensate for, or otherwise mitigate, thesensed noise. At low frequencies, at least some implementations of theAEF present as capacitive in nature. In some implementations, variousfactors such as jitter, thermal variations, and other various circuitcharacteristics can generate noise at low frequencies, including at aresonant frequency formed by an AEF (e.g., an equivalent capacitance ofthe AEF at the resonant frequency) and a filter inductor (and/or othercomponent). In some examples, large noise current can flow through thefilter inductor (and/or other component) into or out of the AEF due tothis resonance, increasing power consumption of the AEF (e.g., such asof an operational amplifier of the AEF). This noise current can alsosaturate the operational amplifier of the AEF, degrading performance ofthe operational amplifier and the overall AEF. In response to theoperational amplifier becoming saturated, in at least some examples theAEF is unable to mitigate the noise and its performance is degraded.Furthermore, in some examples, saturation of the operational amplifierof the AEF can cause the noise to increase in value. In variousexamples, regulatory bodies or other agencies or organizations specify amaximum permitted value for EMI or noise in a system in a certainfrequency range, such as from about 150 kHz to about 108 MHz. Inresponse to the AEF becoming saturated, in at least some examples, theAEF becomes unable to mitigate the noise to maintain a value of thenoise below the maximum permitted value.

At least some aspects of this description provide for an AEF including adamping network. The damping network, in some examples, makes the AEFless capacitive, at least at the resonant frequency of the AEF and thefilter inductor (and/or other component). In at least some examples,making the AEF less capacitive comprises increasing a phase angle ofimpedance of the AEF. For example, an ideal resistor has a purely realimpedance component (e.g., extending in a positive direction along ahorizontal axis of an impedance graph). Similarly, an ideal capacitorhas a purely negative imaginary impedance component (e.g., extending ina negative direction along a vertical axis of an impedance graph). Byadding a circuit element in an injection path of the AEF, with a purelyreal impedance component, or another circuit element having an at leastpartially real impedance component, a phase angle of impedance of theAEF is increased. The circuit element is, in some examples, a dampingnetwork. The increase in phase angle of the impedance of the AEF makesthe AEF appear less capacitive at a node to which the AEF is coupled. Inat least some implementations, the damping network includes a resistor.In other implementations, the damping network includes a resistor and acapacitor, coupled together in parallel or in series. The dampingnetwork, in various implementations, mitigates effects of the resonanceon the AEF to prevent the operational amplifier of the AEF from becomingsaturated. Such mitigation prevents, or reduces an effect of, degradedperformance of the AEF due to the resonance of the AEF and the inductor(and/or other components) in the presence of low frequency noisecomponents. In at least some examples, the resistor of the dampingnetwork makes the AEF less capacitive. The capacitor in turn facilitatesperformance of the AEF in the presence of high frequency noise. Bymaking the AEF less capacitive (e.g., such as at least at the resonantfrequency formed by the AEF and the filter inductor (and/or othercomponents) and/or in the presence of low frequency components of thenoise), effects of the resonance of the AEF and the filter inductor arereduced. Reducing the effects of resonance, in at least some examples,prevents an amplifier of the AEF from becoming saturated (e.g., preventsperformance of the AEF from being degraded due to the resonance in thepresence of the low frequency noise). Limiting the effects of theresonance, such as in the presence of the low frequency noise, issometimes referred to as damping the resonance.

Some approaches exist for damping resonance, such as coupling a resistorin series with the filter inductor to damp the resonance between the AEFand the filter inductor (and/or other components). However, such anapproach places the resistor in a power path of a circuit (e.g., in apower path between a VIN node and a power converter), resulting inincreased power loss as current flows through the resistor. Anotherapproach for damping resonance includes coupling a series combination ofa resistor and capacitor in parallel with an AEF. However, to providesufficient damping, the capacitor is comparatively large in capacitanceand, correspondingly, in size. For example, the capacitor may have acapacitance of about 47 microfarads (uF), which for at least someimplementations of electrolytic capacitors corresponds to a physicalsize of about 10.5 millimeters (mm)×10.5 mm×10.2 mm. Conversely, adamping network according to at least some examples and/orimplementations of this description does not place a component in apower path of an SMPS. Further, a damping network according to at leastsome examples and/or implementations of this description includes acapacitor having a capacitance substantially less than 47 uF, andtherefore smaller in size and less in cost than other approaches fordamping resonance.

Referring to FIG. 1 , a block diagram of an illustrative SMPS 100 isshown. In at least one example, the SMPS 100 includes a controller 102and a power converter 104. The SMPS 100, at least through the powerconverter 104, switches power provided based on a power source 106 froma node 150 to a load 108. The SMPS 100 further includes, or is adaptedto be coupled to, an AEF 164 via a filter 166. The power converter 104is, for example, a buck-boost power converter that is capable ofoperating according to a buck mode of operation, a boost mode ofoperation, and a buck-boost mode of operation. In at least one example,the controller 102 includes, or is adapted to be coupled to, a feedbackcircuit 112, an oscillator 116, a frequency circuit 118, a rampgenerator 120, a comparator 122, a comparator 124, a mode transitioncontrol circuit 126, and a gate driver 128. The SMPS 100 of thisdescription is illustrated and described as implementing average currentmode control over the power converter 104. However, other controlmethods are possible, such as peak current mode control, voltage modecontrol, or any other suitable form of control implemented in a fixedfrequency or variable frequency system.

At least one example of the SMPS 100 includes at least some aspects ofthe controller 102, the power converter 104, and/or the AEF 164 on asame semiconductor die and/or in a same component package, while inother examples the controller 102, the power converter 104, and/or theAEF 164 may be fabricated separately and/or configured or adapted tocouple together. For example, at least some aspects of the controller102 may be fabricated separately and coupled together. Accordingly,while illustrated as including the gate driver 128, in at least oneexample the controller 102 does not include the gate driver 128 andinstead is adapted to be coupled to the gate driver 128. Similarly,other components illustrated as being included in the controller 102 mayinstead be configured to couple, in whole or in part, to the controller102 and not be included on a same semiconductor die and/or in a samecomponent package as the controller 102.

In at least one example, the feedback circuit 112 includes a resistor130 coupled between a node 152 and a node 154 and a resistor 132 coupledbetween the node 154 and a ground node 156. The feedback circuit 112further includes an amplifier 134 having a first input terminal (e.g., anon-inverting input terminal) coupled to a node 158 and configured toreceive a reference voltage (VREF) at the node 158. The amplifier 134further has a second input terminal (e.g., an inverting input terminal)coupled to the node 154, and an output terminal coupled to a node 160. Afeedback signal (FB) exists at the node 154 and is a scaledrepresentation of VOUT, scaled according to a ratio of resistance of theresistor 132 to a total resistance of the resistor 130 and the resistor132. A signal (VC) exists at the node 160, output by the amplifier 134based on a difference between VREF and FB. A resistor 136 is coupledbetween the node 160 and a top plate of a capacitor 138 and a bottomplate of the capacitor 138 is coupled to the ground node 156. Thefeedback circuit 112 further includes a current sense circuit 140 and anamplifier 142. The current sense circuit 140 is adapted to be coupled tothe power converter 104 to generate an output signal (VI) that is avoltage representation of a current flowing through the power converter104. The amplifier 142 has a first input terminal (e.g., a positive ornon-inverting input terminal) coupled to the node 160, a second inputterminal (e.g., a negative or inverting input terminal) coupled to anoutput terminal of the current sense circuit 140, and an output terminalcoupled to a node 162. A current control signal (CC) exists at the node162, output by the amplifier 142 based on a difference between VC andVI. A resistor 144 is coupled between the node 162 and a top plate of acapacitor 146 and a bottom plate of the capacitor 146 is coupled to theground node 156.

The oscillator 116, in at least some examples, is any component orcomponents suitable for generating a clock signal, illustrated in FIG. 1as CLK. A frequency of CLK is determined, in at least some examples,based on a value of a signal received from the frequency circuit 118.For example, the frequency circuit 118 generates a current signal,illustrated in FIG. 1 as ICLK, based at least partially on a value of aresistor 148 coupled to the frequency circuit 118. The frequency circuit118 outputs ICLK to the oscillator 116 to enable the oscillator 116 togenerate CLK at least partially according to ICLK. In at least someexamples, the frequency circuit 118 further outputs ICLK to the rampgenerator 120. The oscillator 116 outputs CLK to, in some examples, theramp generator 120 and the mode transition control circuit 126.

The ramp generator 120, in at least some examples, is any component orcomponents suitable for generating buck and boost ramp signals for usein controlling the power converter 104. In at least some examples, thebuck and boost ramp signals are generated by charging and resetting(e.g., discharging) one or more capacitors (not shown) at a specifiedrate of charge, specified by a current value of a signal charging theone or more capacitors. In at least some examples, based on the receivedCLK and ICLK signals, the ramp generator 120 generates and outputs thebuck ramp signal and the boost ramp signal.

The comparator 122 includes a first input terminal (e.g., a positive ornon-inverting input terminal) coupled to the node 162, a second inputterminal (e.g., a negative or inverting input terminal) coupled to theramp generator 120 and configured to receive the buck ramp signal fromthe ramp generator 120, and an output terminal. The comparator 124includes a first input terminal (e.g., a positive or non-inverting inputterminal) coupled to the node 162, a second input terminal (e.g., anegative or inverting input terminal) coupled to the ramp generator 120and configured to receive the boost ramp signal from the ramp generator120, and an output terminal. In at least some examples, a controlsignal, illustrated in FIG. 1 as PWM_BK, exists at the output terminalof the comparator 122 and a control signal, illustrated in FIG. 1 asPWM_BST, exists at the output terminal of the comparator 124. In someexamples, PWM_BK has an asserted value in response to CC being greaterin value than the buck ramp and a de-asserted value in response to CCbeing less in value than the buck ramp. Similarly, in some examples,PWM_BST has an asserted value in response to CC being greater in valuethan the boost ramp and a de-asserted value in response to CC being lessin value than the boost ramp.

The mode transition control circuit 126 has a plurality of inputterminals configured to receive at least CLK, PWM_BK, PWM_BST, VOUT, andVIN (collectively referred to with respect to the mode transitioncontrol circuit 126 as the received signals). In at least some examples,the mode transition control circuit 126 includes or implements a statemachine to generate one or more control signals for controlling thepower converter 104 according to the received signals. Operation of themode transition control circuit 126 is described in greater detailbelow.

The AEF 164 has an input terminal coupled to the node 170 and an outputterminal coupled to the node 170. The input of the AEF 164 is, in someexamples, referred to as a sense node or a sense input. The output ofthe AEF 164 is, in some examples, referred to as a current injectionnode or a current injection output. The filter 166 has an input terminalcoupled to the node 170 and an output terminal coupled to the node 150.In at least some examples, the power source 106 provides a sourcevoltage (VSOURCE) at the node 170. In at least some examples, the powerconverter 104 generates noise at the input node 150. The filter 166 andthe AEF 164, in at least some examples, mitigate passing of noisepresent at the node 150 to the node 170. Such mitigation also mitigatessubsequent effect(s) of noise present at the node 150 on the powersource 106 (e.g., such as variation in a value of VSOURCE). Accordingly,in at least some examples the AEF 164 includes components suitable forperforming active filtering, such as an amplifier (not shown) and one ormore passive components (not shown). Also, in at least some examples,the filter 166 includes an inductor 172 coupled between the node 170 andthe node 150 and a capacitor 174 coupled between the node 150 and theground node 156.

In at least one example, the SMPS 100 is configured to receive VIN fromthe power source 106 at the node 170 and provide VOUT at the node 152for supplying the load 108. VOUT is based at least partially on VIN aspresent at the node 150 and VREF as received by the SMPS 100 at the node158. VREF may be received from any suitable device (not shown) such as aprocessor, microcontroller, or any other device exerting control overthe SMPS 100 to control a value of VOUT. In at least one example, VREFhas a value representative of a specified (e.g., user-specified, target,preconfigured, programmed, etc.) value of FB. Accordingly, in at leastsome implementations, the controller 102 receives one or more signalsfrom the power converter 104. For example, the controller 102 mayreceive VOUT from the power converter 104 and/or an inductor current(IL) of the power converter 104. In various examples, IL may be a valuedirectly measured from an inductor (not shown) of the power converter104 (or a terminal of another component of the power converter 104 towhich the inductor is also coupled) or a value sensed from a senseelement (not shown) of the power converter 104. The sense element is,for example, a sense resistor, a transistor, or any other component orcombination of components capable of measuring IL of the power converter104 and providing a value representative of IL to the controller 102. Inat least one example, the value representative of IL is provided to thefeedback circuit 112 for generation of VI and VOUT is provided to thefeedback circuit 112 and the mode transition control circuit 126.

In at least one example, the feedback circuit 112 is configured toreceive VREF and VOUT and generate VC indicating a variation in FB fromVREF. VC is referred to in some examples as an error signal. In at leastsome examples, FB is an output of a voltage divider formed of theresistor 130 and the resistor 132, where an input to the voltage divideris VOUT. VC is subsequently filtered by the resistor 136 and thecapacitor 138 before being received by the amplifier 142. The amplifier142, in at least one example, is configured to receive VC and VI andgenerate CC indicating a variation in VI from VC. CC is subsequentlyfiltered by the resistor 144 and the capacitor 146 before being receivedby the comparator 122 and the comparator 124.

As described above, in at least one example, the frequency circuit 118generates and outputs a signal ICLK based on a resistance of theresistor 148. ICLK at least partially determines a frequency of a clocksignal CLK generated and output by the oscillator 116.

The mode transition control circuit 126 receives CLK, PWM_BK, PWM_BST,VOUT, and VIN and generates control signals for controlling the gatedriver 128 to control the power converter 104. In at least one example,the mode transition control circuit 126 includes or otherwise implementsa digital state machine to generate the control signals based on valuesof CLK, PWM_BK, PWM_BST, VOUT, and/or VIN.

Based on the control signals received from the mode transition controlcircuit 126, the gate driver 128 generates gate control signals forcontrolling power transistors of the power converter 104, as describedabove. For example, the gate driver 128 generates gate control signalsthat alternatingly, and selectively, turn the power transistors of thepower converter on and off to energize and de-energize elements such asan inductor and/or a capacitor (each not shown). This energizing andde-energizing provides the buck, boost, and/or buck-boost functionalitydescribed herein. The gate driver 128 is implemented according to anysuitable architecture, the scope of which is not limited herein.

As described above, in at least some examples, the controlling (e.g.,switching) of the power transistors of the power converter 104 (e.g.,the switching on and off) creates noise (e.g., such as high frequencynoise above about 150 kHz) at the node 150. In the absence of the AEF164 and the filter 166, a value of VSOURCE may be altered based on thenoise at the node 150, affecting the performance of other componentsand/or systems not shown in FIG. 1 that also receive VSOURCE or arecoupled to the power source 106. To mitigate effects of the highfrequency noise (e.g., high frequency components of the noise), the AEF164 and the filter 166 filter out the high frequency noise. The noisecreated by the power converter 104 further includes low frequency noise(e.g., low frequency components of the noise). In at least someexamples, the low frequency noise is generated based on jitterassociated with components of the power converter 104, thermalvariations in components of the SMPS 100, and/or other circuitoperational characteristics. In at least some examples, the lowfrequency noise can be at frequencies below about 150 kHz. In somecircumstances, the inductor 172 of the filter 166 and the AEF 164 form aresonant circuit that causes resonance at frequencies below 150 kHz. Theresonance, in at least some examples, causes noise current, sometimeshaving comparatively large values (e.g., as compared to noise currentoutside of resonant frequencies), to flow into the AEF 164 atfrequencies around a resonant frequency. The resonant frequency isdefined according to an inductance of the inductor 172 and an equivalentcapacitance of the AEF 164. In response to the comparatively large noisecurrent flowing into the AEF 164, in some examples, the operationalamplifier of the AEF 164 becomes saturated, affecting and/or degradingperformance of the AEF 164. To mitigate (e.g., dampen) the resonance,the AEF 164 includes a damping network 176. The damping network 176, inat least some examples, makes the AEF 164 less capacitive, as describedabove. Making the AEF 164 less capacitive reduces the noise currentflowing into the operational amplifier of the AEF 164 due to theresonance. In at least some examples, the damping network 176 furtherenables a reduction in ambient noise present at the node 170 bypreventing the AEF 164 from becoming saturated, as described in greaterdetail below with respect to the AEF 200 of FIG. 2 .

Referring to FIG. 2 , a schematic diagram of an illustrative AEF 200 isshown. In at least some examples, the AEF 200 is suitable forimplementation as the AEF 164 of the SMPS 100 of FIG. 1 . Accordingly,reference may be made to components and/or signals of the SMPS 100 indescribing the AEF 200. In other examples, the AEF 200 is suitable forimplementation in any circuit, device, or system in which noise is, ormay be, present and it may be desirable to actively filter that noise.

In at least one implementation, the AEF 200 includes an amplifier (e.g.,such as an operational amplifier) 202 and a damping network 204 suitablefor implementation as the damping network 176. At least partiallybecause the amplifier 202 is powered by a power source, the AEF 200 isconsidered an active filter. This stands in opposition to passivefilters that do not include a component powered by a power source (e.g.,such as a filter including include only passive components such asresistors, capacitors, and/or inductors that are not powered by a powersource to enable their operation). In at least some implementations, theAEF 200 further includes one or more of a capacitor 206, a capacitor208, a resistor 210, a resistor 212, a capacitor 214, a capacitor 216,and/or a resistor 218. In at least some examples, one or more of thecapacitor 206, the capacitor 208, the resistor 210, the resistor 212,the capacitor 214, the capacitor 216, and/or the resistor 218 may beomitted from the AEF 200 to reduce a surface area consumed by the AEF200 and/or a cost of implementing the AEF 200. The components that areomitted are determined, in some examples, according to a specifiedfunction, stability, attenuation, and/or robustness of the AEF 200. Inone implementation, the damping network 204 includes a resistor 220. Inanother implementation, the damping network 204 includes the resistor220 and a capacitor 222.

In an example architecture of the AEF 200, the capacitor 206 is coupledbetween the node 224 and a node 226. The capacitor 208 and the resistor210 are coupled in series between the node 226 and a node 228. Theresistor 212 is coupled between the node 226 and the node 228. Theamplifier 202 has a first input terminal (e.g., a negative or invertinginput terminal) coupled to the node 226 and a second input terminal(e.g., a positive or non-inverting input terminal) coupled to a node234. The amplifier 202 further has an output terminal coupled to thenode 228. The amplifier 202 yet further has a positive supply voltageterminal coupled to a node 232 and a negative supply voltage terminalcoupled to a ground node 236, which has a ground voltage potential in atleast some examples, The damping network 204 is coupled in series withthe capacitor 214 between the node 228 and the node 224. The capacitor216 and the resistor 218 are coupled together in series between the node224 and the ground node 236. The resistor 220 and the capacitor 222 arecoupled in parallel between the node 228 and the node 230. In at leastsome examples, VSOURCE exists at the node 224 and a component supplyvoltage (VCC) exists at the node 232. Further, in at least someexamples, a reference voltage approximately equal to VCC/2 exists at thenode 234.

In at least some examples, all components of the AEF 200 are implementedon a same semiconductor die and/or in a same component package, while inother examples various components of the AEF 200 may be fabricatedseparately and/or configured or adapted to couple together. For example,in some implementations the damping network 204 may not be included on asame semiconductor die and/or in a same component package as one or moreother components of the AEF 200. Accordingly, while illustrated asincluding the damping network 204, in at least one example the AEF 200does not include the damping network 204 and instead is adapted to becoupled to the damping network 204. Similarly, other componentsillustrated as being included in the AEF 200, such as one or more of thecapacitor 206, the capacitor 208, the resistor 210, the resistor 212,the capacitor 214, the capacitor 216, and/or the resistor 218, mayinstead be configured to couple, in whole or in part, to the AEF 200 andnot be included on a same semiconductor die and/or in a same componentpackage as the AEF 200. Yet further, in some examples at least somecomponents of other devices, such as a power converter, filter, etc. maybe on a same semiconductor die and/or in a same component package as atleast some components of the AEF 200, such as the amplifier 202.

The capacitor 206 is, in some examples, a sense capacitor having acapacitance defined as C206 and is configured to enable the amplifier202 to detect, at its first input terminal, noise present at the node224. In at least some examples, C206 is in a range of about 25nanofarads to about 100 nanofarads. The capacitor 208 is, in someexamples, a compensation capacitor having a capacitance defined as C208.The resistor 210 is, in some examples, a compensation resistor having aresistance defined as R210. The resistor 212 is, in some examples, adirect current (DC) feedback resistor that provides DC feedback for theamplifier 202. In at least some examples, the resistor 212 has aresistance in a range of about 50 kiloohms to about 20 megaohms. Thecapacitor 214 is, in some examples, an injection capacitor having acapacitance defined as C214 and is configured to enable the amplifier202 to inject or drive a noise cancellation signal to the node 224. Inat least some examples, C214 is in a range of about 50 nanofarads toabout 1 microfarad. The capacitor 216 is, in some examples, acompensation capacitor having a capacitance defined as C216. Theresistor 218 is, in some examples, a compensation resistor having aresistance defined as R218. The resistor 220 is, in some examples, adamping resistor having a resistance defined as R220. The capacitor 222is, in some examples, a damping capacitor having a capacitance definedas C222.

In an example of operation of the AEF 200, the AEF 200 is configured tosense a voltage of the noise (“noise voltage”) of noise present at thenode 224. In at least some examples, the noise present at the node 224includes low frequency noise components and high frequency noisecomponents. The AEF 200 is further configured to generate a cancellationsignal according to a difference between the sensed noise voltage andthe reference voltage present at the node 234. The AEF 200 is stillfurther configured to inject the cancellation signal into the node 224.

The capacitor 206 and the capacitor 214 each couple, or are configuredto couple, the AEF 200 to the node 224 via alternating current (AC)coupling (e.g., AC couple). For example, the capacitor 206 AC couplesthe first input terminal of the amplifier 202 to the node 224 and thecapacitor 214 couples the node 230 to the node 224. The amplifier 202senses the noise voltage present at the node 224 through the capacitor206. Based on a difference between the sensed noise voltage and thereference voltage present at the node 234, the amplifier 202 generatesthe cancellation signal having an output voltage and an output current.The output current is injected into (or sunk from) the node 224 throughthe capacitor 214, canceling, or otherwise mitigating, at least aportion of the noise voltage and/or the sensed noise voltage. In atleast some examples, the output current is instead injected into (orsunk from) the node 224 through the capacitor 214 and the dampingnetwork 204.

As described above, in at least some examples, an inductor of a filter(not shown) coupled to the AEF 200 and the AEF 200 together resonant ata frequency (often at a low frequency, such as below 150 kHz) definedaccording to an equivalent capacitance of the AEF 200 and an inductanceof the inductor. This resonance leads to increased noise voltage (oftenat a low frequency, such as below 150 kHz) presented at the node 224 atthe resonant frequency and/or at frequencies close to the resonantfrequency. This resonance also leads to a large low frequency currentflowing into the operational amplifier and, in some examples, saturatesthe amplifier 202 (e.g., a magnitude of the voltage present at theoutput terminal of the amplifier 202 and/or a magnitude of the currentflowing into (or out of) the output terminal of the amplifier 202 issufficiently high such that changes to values of input signals of theamplifier 202 will not alter the voltage and/or current present at theoutput terminal of the amplifier 202). In response to the amplifier 202becoming saturated, the amplifier 202 is in a non-linear region ofoperation. The non-linear region of operation reduces gain of theamplifier 202 and, in some examples, clamps a value of the outputvoltage (and/or a value of the output current) based on a supply (notexplicitly shown) powering the amplifier 202. In at least some examples,an ability of the AEF 200 to cancel the noise present at the node 224 isdegraded in response to the amplifier 202 becoming saturated. Ambientnoise present at the node 224, in some examples, increases due toinjection of broadband noise currents into (or sunk from) the node 224by the amplifier 202 in response to the amplifier 202 being saturated.Furthermore, while operating in the non-linear region of operation, aquiescent current of the amplifier 202 increases, in at least someimplementations power consumption of the amplifier 202 and the AEF 200increases.

In at least some examples, the damping network 204 mitigates theincreased low frequency noise due to the resonance at the node 224 andthereby inhibits the amplifier 202 from becoming saturated. For example,the damping network 204 is configured to make the AEF less capacitive,such as in the presence of the low frequency noise components. Toaccomplish this, the damping network 204 introduces impedance having areal component in a path between the output terminal of the amplifier202 and the node 224, making the AEF 200 appear less capacitive from aview of the node 224. This impendence having a real component betweenthe output terminal of the amplifier 202 and the node 224 reduces theoutput current present at the output terminal of the amplifier 202and/or the output voltage present at the output terminal of theamplifier 202. This reduction in output current and/or output voltage,in at least some examples, prevents the amplifier 202 from becomingsaturated, thereby improving noise mitigation of the AEF.

In at least some implementations of the AEF 200, the capacitor 222 maybe omitted. For example, for implementations of the AEF 200 in systemsthat operate at high frequencies (e.g., greater than about 2 megahertz),the capacitor 222 may be omitted such that the damping network 204includes only the resistor 220. In other examples, the capacitor 222 isincluded in the damping network 204 to provide a signal path in thedamping network 204 that is configured to reduce an impact of making theAEF less capacitive on operation of the AEF in the presence of the highfrequency noise components. In at least one implementation of suchexamples, an optimal value (or approximately optimal value) of R220 isdefined according to the following equation 1, in which L is aninductance of an inductor (such as the inductor 172) to which the AEF200 is configured to couple at the node 224.

$\begin{matrix}{{R\; 220} = \sqrt{\frac{\frac{C\; 206}{C\; 208}*L}{C\; 214}}} & (1)\end{matrix}$Increasing a value of R220 above an optimal value as provided for inequation 1, in at least some examples, provides a greater degree ofdamping in the AEF 200. However, this increased damping is at a cost ofoverall performance of the AEF 200, such as an increase to theequivalent impedance of the AEF 200 (e.g., in a particular frequencyrange or band).

In other implementations of the AEF 200, the damping network 204includes both the resistor 220 and the capacitor 222. In at least oneimplementation of such examples, C222 is defined according to thefollowing equation 2 and R220 is defined according to the followingequation 3 in which L is again an inductance of an inductor (such as theinductor 172) to which the AEF 200 is configured to couple at the node224.

$\begin{matrix}{{C\; 222} = \frac{C\; 214}{2}} & (2) \\{{R\; 220} = {\frac{C\; 206}{C\; 208}*\sqrt{\frac{L}{\frac{C\; 206}{C\; 208}*C\; 214}}}} & (3)\end{matrix}$

In at least some examples, the above equations 1, 2, and 3 provideoptimal, or approximately optimal, component values for damping theresonance of the AEF 200 at the resonant frequency defined by theequivalent capacitance of the AEF 200 and the inductor having theinductance of L. In other examples, one or more of the equations 1, 2,and/or 3 are modified according to values of other components of the AEF200 and/or components coupled to the AEF. This damping, in at least someexamples, does not degrade (or has a negligible degrading effect on) theperformance of AEF 200 at high frequencies, such as frequencies above150 kHz. In implementations in which the damping network 204 includesboth the resistor 220 and the capacitor 222, in at least some examplesthe resistor 220 damps the resonance at low frequencies and thecapacitor 222 facilitates noise mitigation of the AEF 200 at highfrequencies. For example, at a frequency of less than about1/(2*π*R220*C222), impedance in the damping network 204 is dominated bythe resistor 220. At a frequency greater than about 1/(2*π*R220*C222),impedance in the damping network 204 is dominated by the capacitor 222.In this way, the damping network 204 both damps the resonance of the AEF200 and the inductor (and/or other components) at low frequency, andalso facilitates performance of AEF 200 at high frequencies.

Referring to FIG. 3 , a diagram 300 of illustrative signal waveforms isshown. In at least some examples, the diagram 300 illustrates an ACsimulation of damping in an AEF, such as the AEF 200 of FIG. 2 .Accordingly, reference may be made to at least some signals and/orcomponents of the AEF 200 in describing the diagram 300. The diagram 300illustrates damping in the AEF 200 in implementations in which thedamping network 204 includes the resistor 220 and does not include thecapacitor 222. A horizontal axis of the diagram 300 is representative offrequency in a unit of hertz (Hz) and a vertical axis of the diagram 300is representative of current in a unit of amperes (A).

The diagram 300 includes two signals. Signal 305 represents currentflowing into the output terminal of the amplifier 202 in the absence ofthe damping network 204. Signal 310 represents current flowing into theoutput terminal of the amplifier 202 in the presence of the dampingnetwork 204 including the resistor 220 having a resistance determinedaccording to equation 1. Both the signal 305 and the signal 310correspond to an assumed AC excitation having a peak current value ofabout 1A. As illustrated by the signal 305, in the absence of thedamping network 204, a current having a peak value of about 6.5 A wouldflow through the output terminal of the amplifier 202 at a resonantfrequency of the AEF 200 and a filter inductor, as described in greaterdetail above. However, as illustrated by the signal 310, inimplementations in which the AEF 200 includes the damping network 204,the current flowing through the output terminal of the amplifier 202 islimited to a peak value of about 0.5 A. In this example, the resistor220 makes the AEF 200 less capacitive, thereby damping the resonance ofthe AEF 200 and the filter inductor and limiting the peak current of thecurrent flowing through the output terminal of the amplifier 202.Accordingly, in at least some examples this damping prevents saturationof the amplifier 202 and the AEF 200, as described in greater detailabove.

Referring to FIG. 4 , a diagram 400 of illustrative signal waveforms isshown. In at least some examples, the diagram 400 illustrates an ACsimulation of damping in an AEF, such as the AEF 200 of FIG. 2 .Accordingly, reference may be made to at least some signals and/orcomponents of the AEF 200 in describing the diagram 400. The diagram 400illustrates damping in the AEF 200 in implementations in which thedamping network 204 includes both the resistor 220 and the capacitor222. A horizontal axis of the diagram 400 is representative of frequencyin a unit of hertz (Hz) and a vertical axis of the diagram 400 isrepresentative of current in a unit of amperes (A).

The diagram 400 includes three signals. Signal 405 represents currentflowing into the output terminal of the amplifier 202 in the absence ofthe damping network 204. Signal 410 represents current flowing into theoutput terminal of the amplifier 202 in the presence of the dampingnetwork 204 in implementations in which the damping network 204 includesinfinite resistance. Signal 415 represents current flowing into theoutput terminal of the amplifier 202 in implementations in which thedamping network 204 includes both the resistor 220 and the capacitor222, having respective resistance and capacitance values selectedaccording to equation 3 and equation 2. Each of the signals 405, 410,and 415 correspond to an assumed AC excitation having a peak currentvalue of about 1A. As illustrated by the signal 405, a current having apeak value greater than about 3A would flow through the output terminalof the amplifier 202 at a resonant frequency of the AEF 200 and a filterinductor, as described in greater detail above. As illustrated by thesignal 410, in implementations in which the damping network 204 includesinfinite resistance, a current having a peak value greater than about 3Awould flow through the output terminal of the amplifier 202 at anotherresonant frequency of the AEF 200 and the filter inductor, as describedin greater detail above. However, as illustrated by the signal 415, inimplementations in which the AEF 200 includes the damping network 204including both the resistor 220 and the capacitor 222, having respectiveresistance and capacitance values selected according to equation 3 andequation 2, a current having a peak value of about 0.5 A would flowthrough the output terminal of the amplifier 202. In this example, theresistor 220 makes the AEF 200 less capacitive, thereby damping theresonance of the AEF 200 and the filter inductor and limiting the peakcurrent of the current flowing through the output terminal of theamplifier 202. Accordingly, in at least some examples this dampingprevents saturation of the AEF 200, as described in greater detailabove. At high frequencies, the capacitor 222 dominates impedancepresent in the damping network 204, reducing the phase angle of theimpedance of the damping network of the AEF 200, thereby facilitatingperformance of AEF 200 at high frequencies.

While various examples and/or implementations are described herein withrespect to reducing noise generated generate in a SMPS and/or byswitching of power transistors in a power converter, other examples ofan AEF including damping network, as disclosed herein, are applicable tonoise suppression in a wide variety of applications, such as motordrives, class—D amplifiers, etc.

The term “couple” is used throughout the specification. The term maycover connections, communications, or signal paths that enable afunctional relationship consistent with the description of thisdescription. For example, if device A generates a signal to controldevice B to perform an action, in a first example device A is coupled todevice B, or in a second example device A is coupled to device B throughintervening component C if intervening component C does notsubstantially alter the functional relationship between device A anddevice B such that device B is controlled by device A via the controlsignal generated by device A. A device that is “configured to” perform atask or function may be configured (e.g., programmed and/or hardwired)at a time of manufacturing by a manufacturer to perform the functionand/or may be configurable (or re-configurable) by a user aftermanufacturing to perform the function and/or other additional oralternative functions. The configuring may be through firmware and/orsoftware programming of the device, through a construction and/or layoutof hardware components and interconnections of the device, or acombination thereof. Furthermore, a circuit or device that is describedherein as including certain components may instead be adapted to becoupled to those components to form the described circuitry or device.For example, a structure described as including one or moresemiconductor elements (such as transistors), one or more passiveelements (such as resistors, capacitors, and/or inductors), and/or oneor more sources (such as voltage and/or current sources) may insteadinclude only the semiconductor elements within a single physical device(e.g., a semiconductor die and/or integrated circuit (IC) package) andmay be adapted to be coupled to at least some of the passive elementsand/or the sources to form the described structure either at a time ofmanufacture or after a time of manufacture, for example, by an end-userand/or a third-party.

While certain components may be described herein as being of aparticular process technology, these components may be exchanged forcomponents of other process technologies. Circuits described herein arereconfigurable to include the replaced components to providefunctionality at least partially similar to functionality availableprior to the component replacement. Components illustrated as resistors,unless otherwise stated, are generally representative of any one or moreelements coupled in series and/or parallel to provide an amount ofimpedance represented by the illustrated resistor. For example, aresistor or capacitor illustrated and described herein as a singlecomponent may instead be multiple resistors or capacitor, respectively,coupled in parallel between the same nodes. As another example, aresistor or capacitor illustrated and described herein as a singlecomponent may instead be multiple resistors or capacitor, respectively,coupled in series between the same two nodes as the single resistor orcapacitor. Also, uses of the phrase “ground voltage potential” in theforegoing description include a chassis ground, an Earth ground, afloating ground, a virtual ground, a digital ground, a common ground,and/or any other form of ground connection applicable to, or suitablefor, the teachings of this description. Unless otherwise stated,“about”, “approximately”, or “substantially” preceding a value means+/−10 percent of the stated value.

Modifications are possible in the described embodiments, and otherembodiments are possible, within the scope of the claims.

What is claimed is:
 1. A circuit comprising: an amplifier having an amplifier output and first and second amplifier inputs, the first amplifier input coupled to a voltage input terminal, and the second amplifier input directly connected to a reference voltage terminal; a feedback circuit including a first resistor and a first capacitor connected in series between the amplifier output and the first amplifier input, and a second resistor directly connected between the first amplifier input and the amplifier output; a damping circuit having a damping circuit input and a damping circuit output, the damping circuit input directly connected to the amplifier output, the damping circuit including a third resistor and a second capacitor coupled in parallel between the damping circuit input and the damping circuit output; and a third capacitor directly connected between the damping circuit output and the voltage input terminal; wherein the circuit is configured to generate a cancellation signal responsive to a difference between a noise voltage at the voltage input terminal and a voltage at the reference voltage terminal, and to inject the cancellation signal into the voltage input terminal.
 2. The circuit of claim 1, further comprising a fourth capacitor connected between the voltage input terminal and the first amplifier input.
 3. The circuit of claim 2, further comprising a fifth capacitor and a fourth resistor connected in series between the voltage input terminal and a ground terminal.
 4. The circuit of claim 1, wherein the first amplifier input is an inverting input.
 5. A circuit comprising: an amplifier having an amplifier output and first and second amplifier inputs, the first amplifier input coupled to a voltage input terminal, and the second amplifier input directly connected to a reference voltage terminal; a damping circuit having a resistor and a first capacitor connected in parallel, the resistor and the first capacitor each having respective first and second terminals, the respective first terminals of the resistor and first capacitor directly connected to the amplifier output; and a second capacitor directly connected between the voltage input terminal and the respective second terminals of the resistor and the first capacitor; wherein the circuit is configured to generate a cancellation signal responsive to a difference between a noise voltage at the voltage input terminal and a voltage at the reference voltage terminal, and to inject the cancellation signal into the voltage input terminal.
 6. The circuit of claim 5, further comprising a third capacitor coupled between the voltage input terminal and the first amplifier input.
 7. The circuit of claim 5, wherein the resistor is a first resistor, and the circuit further comprises a third capacitor and a second resistor coupled in series between the amplifier output and the amplifier input.
 8. The circuit of claim 5, wherein the resistor is a first resistor, and the circuit further comprises: a second resistor coupled between the amplifier output and the amplifier input; and a third capacitor and a third resistor coupled in series between the amplifier output and the amplifier input.
 9. A circuit comprising: an amplifier having an amplifier output and an amplifier input; a damping circuit including a resistor having a resistance R, and having a first resistor terminal directly connected to the amplifier output, and having a second resistor terminal; a first capacitor having a first terminal directly connected to the second resistor terminal and having a second terminal; a second capacitor directly connected between the second terminal of the first capacitor and the amplifier input; a feedback circuit directly connected between the amplifier output and the amplifier input, the feedback circuit including a third capacitor; and a filter circuit including an inductor having a first inductor terminal coupled to the second terminal of the first capacitor; wherein, ${R = \sqrt{\frac{\frac{C1}{C2}*L}{C3}}},$ where C1 is a capacitance of the second capacitor, C2 is a capacitance of the third capacitor, C3 is a capacitance of the first capacitor, and L is an inductance of the inductor.
 10. The circuit of claim 9, wherein the damping circuit further includes a fourth capacitor coupled in parallel with the resistor.
 11. The circuit of claim 9, wherein the inductor includes a second inductor terminal, and the filter circuit includes a fourth capacitor coupled to the second inductor terminal.
 12. The circuit of claim 9, wherein the inductor includes a second inductor terminal, and the circuit further comprises a power converter having an input coupled to the second inductor terminal.
 13. The circuit of claim 9, wherein the resistor is a first resistor, and the feedback circuit further includes a second resistor coupled in series with the third capacitor between the amplifier output and the amplifier input.
 14. The circuit of claim 9, wherein: the damping circuit further includes a fourth capacitor coupled in parallel with the resistor; the fourth capacitor has a capacitance of ${C = \frac{C1}{2}},$ where C1 is a capacitance of the first capacitor; and the resistor has a resistance of ${R = {\frac{C2}{C3}*\sqrt{\frac{L}{\frac{C2}{C3}*C1}}}},$ where C1 is the capacitance of the first capacitor, C2 is a capacitance of the second capacitor, C3 is a capacitance of the third capacitor, and L is an inductance of the inductor. 